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Low Distortion Mixer AD831
FEATURES Doubly Balanced Mixer Low Distortion +24 dBm Third Order Intercept (IP3) +10 dBm 1 dB Compression Point Low LO Drive Required: 10 dBm Bandwidth 500 MHz RF and LO Input Bandwidths 250 MHz Differential Current IF Output DC to >200 MHz Single-Ended Voltage IF Output Single- or Dual-Supply Operation DC Coupled Using Dual Supplies All Ports May Be DC Coupled No Lower Frequency Limit--Operation to DC User-Programmable Power Consumption APPLICATIONS High Performance RF/IF Mixer Direct to Baseband Conversion Image-Reject Mixers I/Q Modulators and Demodulators FUNCTIONAL BLOCK DIAGRAM
building a quadrature-amplitude modulator or image reject mixer, the differential current outputs of two AD831s may be summed by connecting them together. An integral low noise amplifier provides a single-ended voltage output and can drive such low impedance loads as filters, 50 amplifier inputs, and A/D converters. Its small signal bandwidth exceeds 200 MHz. A single resistor connected between pins OUT and FB sets its gain. The amplifier's low dc offset allows its use in such direct-coupled applications as direct-to-baseband conversion and quadrature-amplitude demodulation. The mixer's SSB noise figure is 10.3 dB at 70 MHz using its output amplifier and optimum source impedance. Unlike passive mixers, the AD831 has no insertion loss and does not require an external diplexer or passive termination. A programmable-bias feature allows the user to reduce power consumption, with a reduction in the 1 dB compression point and third-order intercept. This permits a tradeoff between dynamic range and power consumption. For example, the AD831 may be used as a second mixer in cellular and two-way radio base stations at reduced power while still providing a substantial performance improvement over passive solutions.
PRODUCT HIGHLIGHTS
PRODUCT DESCRIPTION
The AD831 is a low distortion, wide dynamic range, monolithic mixer for use in such applications as RF to IF downconversion in HF and VHF receivers, the second mixer in DMR base stations, direct-to-baseband conversion, quadrature modulation and demodulation, and doppler shift detection in ultrasound imaging applications. The mixer includes an LO driver and a low noise output amplifier and provides both user-programmable power consumption and third order intercept point. The AD831 provides a +24 dBm third order intercept point for 10 dBm LO power, thus improving system performance and reducing system cost compared to passive mixers, by eliminating the need for a high power LO driver and its attendant shielding and isolation problems. The RF, IF, and LO ports may be dc or ac coupled when the mixer is operating from ±5 V supplies or ac coupled when operating from a single-supply of 9 V minimum. The mixer operates with RF and LO inputs as high as 500 MHz. The mixer's IF output is available as either a differential current output or a single-ended voltage output. The differential output is from a pair of open collectors and may be ac coupled via a transformer or capacitor to provide a 250 MHz output bandwidth. In downconversion applications, a single capacitor connected across these outputs implements a low-pass filter to reduce harmonics directly at the mixer core, simplifying output filtering. When REV. C
Information furnished by Analog Devices is believed to be accurate and reliable. However, no responsibility is assumed by Analog Devices for its use, nor for any infringements of patents or other rights of third parties that may result from its use. No license is granted by implication or otherwise under any patent or patent rights of Analog Devices. Trademarks and registered trademarks are the property of their respective companies.
1. 10 dBm LO Drive for a +24 dBm Output Referred Third Order Intercept Point 2. Single-Ended Voltage Output 3. High Port-to-Port Isolation 4. No Insertion Loss 5. Single- or Dual-Supply Operation 6. 10.3 dB Noise Figure
One Technology Way, P Box 9106, Norwood, MA 02062-9106, U.S.A. .O. Tel: 781/329-4700 www.analog.com Fax: 781/326-8703 © 2003 Analog Devices, Inc. All rights reserved.
AD831SPECIFICATIONS
Parameter RF INPUT Bandwidth 1 dB Compression Point Common-Mode Range Bias Current DC Input Resistance Capacitance IF OUTPUT Bandwidth Conversion Gain Output Offset Voltage Slew Rate Output Voltage Swing Short Circuit Current LO INPUT Bandwidth Maximum Input Level Common-Mode Range Minimum Switching Level Bias Current Resistance Capacitance ISOLATION BETWEEN PORTS LO-to-RF LO-to-IF RF-to-IF DISTORTION AND NOISE Third Order Intercept Second Order Intercept 1 dB Compression Point Noise Figure, SSB POWER SUPPLIES Recommended Supply Range Quiescent Current*
*Quiescent current is programmable. Specifications subject to change without notice.
(TA = +25C and VS = 5 V unless otherwise noted; all values in dBm assume 50 load.)
Min Typ 400 10 160 1.3 2 Max Unit MHz dBm V µA k pF
Conditions 10 dBm Signal Level, IP3 +20 dBm 10.7 MHz IF and High Side Injection See Figure 1 DC Coupled Differential or Common Mode
±1 500
Single-Ended Voltage Output, 3 dB Level = 0 dBm, RL = 100 Terminals OUT and VFB Connected DC Measurement; LO Input Switched ±1 RL = 100 , Unity Gain
40
200 0 +15 300 ±1.4 75 400
+40
MHz dB mV V/µs V mA MHz
10 dBm Input Signal Level 10.7 MHz IF and High Side Injection Differential Input Signal DC Coupled Differential or Common Mode
1 1
200 17 500 2 70 30 45 24 62 10 10.3 14
+1 +1 50
V V mV p-p µA pF dB dB dB dBm dBm dBm dB dB
LO = 100 MHz, RS = 50 , 10.7 MHz IF LO = 100 MHz, RS = 50 , 10.7 MHz IF RF = 100 MHz, RS = 50 , 10.7 MHz IF LO = 10 dBm, f = 100 MHz, IF = 10.7 MHz Output Referred, ±100 mV LO Input Output Referred, ±100 mV LO Input RL = 100 , RBIAS = Matched Input, RF = 70 MHz, IF = 10.7 MHz Matched Input, RF = 150 MHz, IF = 10.7 MHz Dual Supply Single Supply For Best Third Order Intercept Point Performance BIAS Pin Open Circuited ±4.5 9
100
±5.5 11 125
V V mA
2
REV. C
AD831
ABSOLUTE MAXIMUM RATINGS1
Supply Voltage ±VS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . ±5.5V Input Voltages RFHI, RFLO . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . ±3 V LOHI, LOLO . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . ±1 V Internal Power Dissipation2 . . . . . . . . . . . . . . . . . . . . 1200 mW Operating Temperature Range AD831A . . . . . . . . . . . . . . . . . . . . . . . . . . . . 40°C to +85°C Storage Temperature Range . . . . . . . . . . . . . . 65°C to +150°C Lead Temperature Range (Soldering 60 sec) . . . . . . . . . . 300°C
NOTES 1 Stresses above those listed under Absolute Maximum Ratings may cause permanent damage to the device. This is a stress rating only and functional operation of the device at these or any other conditions above those indicated in the operational section of this specification is not implied. Exposure to absolute maximum rating conditions for extended periods may affect device reliability. 2 Thermal Characteristics: 20-Lead PLCC Package: JA = 110°C/W; JC = 20°C/W. Note that the JA = 110°C/W value is for the package measured while suspended in still air; mounted on a PC board, the typical value is JA = 90°C/W due to the conduction provided by the AD831's package being in contact with the board, which serves as a heat sink.
ORDERING GUIDE
Model AD831AP AD831AP-REEL7 AD831AP-EB
Temperature Range 40°C to +85°C 40°C to +85°C
Package Description 20-Lead PLCC 20-Lead PLCC Evaluation Board
Package Option P-20A P-20A
PIN DESCRIPTION
Pin No. 1 2 3 4 5 6 7 8 9 10 11 12 13 14 15 16 17 18 19 20
Mnemonic VP IFN AN GND VN RFP RFN VN VP LON LOP VP GND BIAS VN OUT VFB COM AP IFP
Description Positive Supply Input Mixer Current Output Amplifier Negative Input Ground Negative Supply Input RF Input RF Input Negative Supply Input Positive Supply Input Local Oscillator Input Local Oscillator Input Positive Supply Input Ground Bias Input Negative Supply Input Amplifier Output Amplifier Feedback Input Amplifier Output Common Amplifier Positive Input Mixer Current Output
PIN CONFIGURATION 20-Lead PLCC
CAUTION ESD (electrostatic discharge) sensitive device. Electrostatic charges as high as 4000V readily accumulate on the human body and test equipment and can discharge without detection. Although the AD831 features proprietary ESD protection circuitry, permanent damage may occur on devices subjected to high energy electrostatic discharges. Therefore, proper ESD precautions are recommended to avoid performance degradation or loss of functionality.
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3
AD831Typical Performance Characteristics
65
SECOND ORDER INTERCEPT (dBm)
64
63
62
61
60 10
100 FREQUENCY (MHz)
1000
TPC 1. Third Order Intercept vs. Frequency, IF Held Constant at 10.7 MHz
80 70 60
TPC 4. Second Order Intercept vs. Frequency
90 80 70
ISOLATION (dB)
50 40 30 20 10 0 10
ISOLATION (dB)
60 50 40 30 20 10
100 FREQUENCY (MHz)
1000
0 10
100
FREQUENCY (MHz)
1000
TPC 2. IF-to-RF Isolation vs. Frequency
60
TPC 5. LO-to-RF Isolation vs. Frequency
80
2 x LO IF
50
FREQUENCY (dB)
3 x RF IF
70 60 50 40 30 20
3 x RF IF
2 x RF IF
3 x LO IF
ISOLATION (dB)
40
2 x RF IF
RF IF
LO
30
20
RF IF
10
10 0 10
0 10
100 FREQUENCY (MHz)
1000
100 FREQUENCY (MHz)
1000
TPC 3. LO-to-IF Isolation vs. Frequency
TPC 6. RF-to-IF Isolation vs. Frequency
4
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AD831
12
1.00 0.75
THIRD ORDER INTERCEPT (dBm)
1dB COMPRESSION POINT (dBm)
10
0.50 0.25 0.00 0.25 0.50 0.75 1.00 10
8
6
4
2
0 10
100 FREQUENCY (MHz)
1000
100
FREQUENCY (MHz)
1000
TPC 7. 1 dB Compression Point vs. Frequency, Gain = 1
12
TPC 10. Gain Error vs. Frequency, Gain = 1
9 8
1dB COMPRESSION POINT (dBm)
THIRD ORDER INTERCEPT (dBm)
10
7 6 5 4 3 2 1 0 10 100
FREQUENCY (MHz)
8
6
4
2
0 10
100 FREQUENCY (MHz)
1000
1000
TPC 8. 1 dB Compression Point vs. RF Input, Gain = 2
TPC 11. 1 dB Compression Point vs. Frequency, Gain = 4
11
VS = 9V
THIRD ORDER INTERCEPT (dBm)
10
VS = 8V
9
8
LO LEVEL = 10dBm IF = 10.7MHz
7
0
100
200
300
400
500
600
FREQUENCY (MHz)
TPC 9. Third Order Intercept vs. Frequency, LO Held Constant at 241 MHz
TPC 12. Input 1 dB Compression Point vs. Frequency, Gain = 1, 9 V Single Supply
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AD831
1200
1000
INPUT RESISTANCE ()
INPUT RESISTANCE
4.0
600
3.0
400
2.5
200
2.0
0 50
100
150
200
250
FREQUENCY (MHz)
TPC 13. Input Third Order Intercept, 9 V Single Supply
TPC 15. Input Impedance vs. Frequency, ZIN = R C
18
17
16
15
NOISE FIGURE (dB)
14 13 12 11 10 9
8 50
100
150 FREQUENCY (MHz)
200
250
TPC 14. Input Second Order Intercept, 9 V Single Supply
TPC 16. Noise Figure vs. Frequency, Matched Input
6
REV. C
INPUT CAPACITANCE
INPUT CAPACITANCE
800 3.5
AD831
THEORY OF OPERATION
The AD831 consists of a mixer core, a limiting amplifier, a low noise output amplifier, and a bias circuit (Figure 1). The mixer's RF input is converted into differential currents by a highly linear, Class A voltage-to-current converter, formed by transistors Q1, Q2 and resistors R1, R2. The resulting currents drive the differential pairs Q3, Q4 and Q5, Q6. The LO input is through a high gain, low noise limiting amplifier that converts the 10 dBm LO input into a square wave. This square wave drives the differential pairs Q3, Q4 and Q5, Q6 and produces a high level output at IFP and IFN--consisting of the sum and difference frequencies of the RF and LO inputs--and a series of lower level outputs caused by odd harmonics of the LO frequency mixing with the RF input. An on-chip network supplies the bias current to the RF and LO inputs when these are ac-coupled; this network is disabled when the AD831 is dc-coupled.
When the integral output amplifier is used, pins IFN and IFP are connected directly to pins AFN and AFP; the on-chip load resistors convert the output current into a voltage that drives the output amplifier. The ratio of these load resistors to resistors R1, R2 provides nominal unity gain (0 dB) from RF-to-IF. The expression for the gain, in decibels, is Ê 4 ^ Ê 1^ Ê p ^ GdB = 20 log10 Á ~ Á ~ Á ~ Ë p ¯Ë 2¯Ë 2 ¯ where: 4 is the amplitude of the fundamental component of a p squarewave. 1 is the conversion loss. 2 p is the small signal dc gain of the AD831 when the LO input 2 is driven fully positive or negative. (1)
Figure 1. Simplified Schematic Diagram
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AD831
The mixer has two open-collector outputs (differential currents) at pins IFN and IFP. These currents may be used to provide nominal unity RF to IF gain by connecting a center-tapped transformer (1:1 turns ratio) to pins IFN and IFP as shown in Figure 2.
Low-Pass Filtering
A simple low-pass filter may be added between the mixer and the output amplifier by shunting the internal resistive loads (an equivalent resistance of about 14 with a tolerance of 20%) with external capacitors; these attenuate the sum component in a downconversion application (Figure 4). The corner frequency of this one-pole low-pass filter (f = (2 RCF ) 1) should be placed about an octave above the difference frequency IF. Thus, for a 70 MHz IF, a 3 dB frequency of 140 MHz might be chosen, using CF = (2 14 140 MHz) 1 82 pF, the nearest standard value.
Figure 2. Connections for Transformer Coupling to the IF Output Programming the Bias Current
Because the AD831's RF port is a Class-A circuit, the maximum RF input is proportional to the bias current. This bias current may be reduced by connecting a resistor from the BIAS pin to the positive supply (Figure 3). For normal operation, the BIAS pin is left unconnected. For lowest power consumption, the BIAS pin is connected directly to the positive supply. The range of adjustment is 100 mA for normal operation to 45 mA total current at minimum power consumption.
Figure 4. Low-Pass Filtering Using External Capacitors Using the Output Amplifier
The AD831's output amplifier converts the mixer core's differential current output into a single-ended voltage and provides an output as high as ±1 V peak into a 50 V load (+10 dBm). For unity gain operation (Figure 5), the inputs AN and AP connect to the opencollector outputs of the mixer's core and OUT connects to VFB.
Figure 3. Programming the Quiescent Current Figure 5. Output Amplifier Connected for Unity Gain Operation
8
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AD831
For gains other than unity, the amplifier's output at OUT is connected via an attenuator network to VFB; this determines the overall gain. Using resistors R1 and R2 (Figure 6), the gain setting expression is GdB Ê R1 + R2 ^ = 20 log10 Á ~ Ë R2 ¯
(2)
Figure 7. Connections for Driving a Doubly Terminated Band-Pass Filter
Figure 6. Output Amplifier Feedback Connections for Increasing Gain Driving Filters
Higher gains can be achieved, using different resistor ratios, but with concomitant reduction in the bandwidth of this amplifier (Figure 8). Note also that the Johnson noise of these gain setting resistors, as well as that of the BPF terminating resistors, is ultimately reflected back to the mixer's input; thus they should be as small as possible, consistent with the permissible loading on the amplifier's output.
12 G =1
1dB COMPRESSION POINT (dBm)
The output amplifier can be used for driving reverse-terminated loads. When driving an IF band-pass filter (BPF), for example, proper attention must be paid to providing the optimal source and load terminations so as to achieve the specified filter response. The AD831's wideband highly linear output amplifier affords an opportunity to increase the RF to IF gain to compensate for a filter's insertion and termination losses. Figure 7 indicates how the output amplifier's low impedance (voltage source) output can drive a doubly terminated band-pass filter. The typical 10 dB of loss (4 dB of insertion loss and 6 dB due to the reverse-termination) be made up by the inclusion of a feedback network that increases the gain of the amplifier by 10 dB (3.162). When constructing a feedback circuit, the signal path between OUT and VFB should be as short as possible.
10 G =2 8 G =4
6
4
2 0 10
100 FREQUENCY (MHz)
1000
Figure 8. Output Amplifier 1 dB Compression Point for Gains of 1, 2, and 4 (Gains of 0 dB, 6 dB, and 12 dB, Respectively)
REV. C
9
AD831
APPLICATIONS
Careful component selection, circuit layout, power supply dc coupling, and shielding are needed to minimize the AD831's susceptibility to interference from radio and TV stations, etc. In bench evaluation, we recommend placing all of the components in a shielded box and using feedthrough decoupling networks for the supply voltage. Circuit layout and construction are also critical, since stray capacitances and lead inductances can form resonant circuits and are a potential source of circuit peaking, oscillation, or both.
Dual-Supply Operation
Figure 9 shows the connections for dual-supply operation. Supplies may be as low as ±4.5 V but should be no higher than ±5.5 V, due to power dissipation.
The RF input to the AD831 is shown connected by an impedance matching network for an assumed source impedance of 50 . TPC 15 shows the input impedance of the AD831 plotted vs. frequency. The input circuit can be modeled as a resistance in parallel with a capacitance. The 82 pF capacitors (CF ) connected from IFN and IFP to VP provide a low-pass filter with a cutoff frequency of approximately 140 MHz in down-conversion applications (see the Theory of Operation section for more details). The LO input is connected single-ended because the limiting amplifier provides a symmetric drive to the mixer. To minimize intermodulation distortion, connect pins OUT and VFB by the shortest possible path. The connections shown are for unity-gain operation. At LO frequencies less than 100 MHz, the AD831's LO power may be as low as 20 dBm for satisfactory operation. Above 100 MHz, the specified LO power of 10 dBm must be used.
Figure 9. Connections for ±5 V Dual-Supply Operation Showing Impedance Matching Network and Gain of 2 for Driving Reverse-Terminated IF Filter
10
REV. C
AD831
Single-Supply Operation
Figure 10 is similar to the dual-supply circuit in Figure 9. Supplies may be as low as 9 V but should not be higher than 11 V, due to power dissipation. As in Figure 9, both the RF and LO ports are driven single-ended and terminated.
In single-supply operation, the COM terminal is the "ground" reference for the output amplifier and must be biased to half the supply voltage, which is done by resistors R1 and R2. The OUT pin must be ac-coupled to the load.
Figure 10. Connections for +9 V Single-Supply Operation
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AD831
Connections Quadrature Demodulation
Two AD831 mixers may have their RF inputs connected in parallel and have their LO inputs driven in phase quadrature (Figure 11) to provide demodulated in-phase (I) and quadrature (Q) outputs.
The mixers' inputs may be connected in parallel and a single termination resistor used if the mixers are located in close proximity on the PC board.
Figure 11. Connections for Quadrature Demodulation
12
REV. C
AD831
Table I. AD831 Mixer Table, 4.5 V Supplies, LO = 9 dBm
LO Level RF Level Temperature Ambient Dut Supply VPOS Current VNEG Current
9.0 dBm, LO Frequency 130.7 MHz, Data File imdTB10771 0.0 dBm, RF Frequency 120 MHz ±4.50 V 90 mA 91 mA
Intermodulation table RF harmonics (rows) LO harmonics (columns). First row absolute value of nRF mLO, and second row is the sum. 0 0 1 2 3 4 5 6 7 31.6 31.6 45.3 45.3 54.5 54.5 67.1 67.1 53.5 53.5 73.6 73.6 73.8 73.8 1 32.7 32.7 0.0 28.5 48.2 42.4 57.1 65.5 63.1 53.6 62.6 68.4 57.7 73.5 73.9 73.8 2 35.7 35.7 37.2 26.7 39.4 49.4 57.5 46.0 69.9 72.9 73.8 70.8 68.6 72.7 63.4 73.2 3 21.1 21.1 41.5 28.0 57.6 42.5 50.6 63.7 69.9 71.2 72.3 72.8 73.1 73.5 72.6 73.8 4 11.6 11.6 30.4 27.2 44.9 51.1 62.6 60.6 69.6 70.1 70.7 73.4 73.8 73.6 74.6 72.6 5 19.2 19.2 34.3 33.2 42.4 46.2 55.8 69.6 74.1 72.6 71.1 73.2 73.0 73.1 74.9 73.7 6 35.1 35.1 25.2 34.3 40.2 58.1 59.7 72.7 69.7 73.5 74.3 73.3 72.9 72.4 73.6 73.5 7 41.9 41.9 40.1 44.8 40.2 61.6 55.2 73.5 58.6 72.7 73.0 72.5 74.4 73.7 74.5 72.9
Table II. AD831 Mixer Table, 5 V Supplies, LO = 9 dBm
LO Level RF Level Temperature Ambient Dut Supply VPOS Current VNEG Current
9.0 dBm, LO Frequency 130.7 MHz, Data File imdTB13882 0.0 dBm, RF Frequency 120 MHz ±5.00 V 102 mA 102 mA
Intermodulation table RF harmonics (rows) LO harmonics (columns). First row absolute value of nRF mLO, and second row is the sum. 0 0 1 2 3 4 5 6 7
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1 36.5 36.5
2 46.5 46.5 41.2 38.7 47.6 35.7 67.0 50.0 48.7 48.1 54.1 62.4 53.6 67.2 37.8 66.3
3 33.0 33.0 41.1 22.9 61.5 38.4 43.0 48.9 64.6 58.4 54.1 67.3 66.5 67.5 54.6 72.9 13
4 17.0 17.0 38.5 28.4 53.7 42.3 60.9 57.8 53.5 56.1 53.7 67.0 58.8 72.9 62.5 71.4
5 23.0 23.0 29.0 35.3 43.5 53.7 47.9 57.0 55.7 63.8 57.9 69.4 63.3 71.2 71.7 70.7
6 34.2 34.2 31.7 34.3 41.5 52.8 50.7 71.8 53.5 70.5 66.6 73.2 61.7 71.7 55.2 72.1
7 45.6 45.6 47.4 52.4 41.8 66.3 41.0 67.4 51.1 67.6 64.3 72.9 71.4 73.2 57.1 73.1
37.5 37.5 45.9 45.9 46.4 46.4 45.1 45.1 35.2 35.2 63.4 63.4 67.3 67.3
0.0 29.1 45.2 39.4 53.0 40.0 56.0 39.0 45.3 53.0 41.1 66.3 65.8 61.6
AD831
Table III. AD831 Mixer Table, 3.5 V Supplies, LO = 20 dBm
LO Level 20.0 dBm, LO Frequency 130.7 MHz, Data File G1T1K 0771 RF Level 0.0 dBm, RF Frequency 120 MHz Temperature Ambient Dut Supply ±3.50 V VPOS Current 55 mA VNEG Current 57 mA Intermodulation table RF harmonics (rows) LO harmonics (columns). First row absolute value of nRF mLO, and second row is the sum. 0 0 1 2 3 4 5 6 7 30.3 30.3 50.3 50.3 48.4 48.4 66.7 66.7 66.9 66.9 78.0 78.0 78.4 78.4 1 45.2 45.2 0.0 29.7 49.4 41.0 55.7 52.9 59.7 65.9 71.5 76.3 69.7 78.3 78.5 78.3 2 35.7 35.7 33.7 28.2 47.4 51.4 58.2 50.0 67.2 78.1 73.6 78.1 76.7 78.3 76.9 78.2 3 16.1 16.1 47.9 24.4 49.9 34.7 45.0 64.5 62.8 74.2 77.6 78.2 78.6 78.2 78.7 78.2 4 21.6 21.6 37.5 26.0 48.8 49.8 57.0 62.8 58.2 77.5 70.8 78.1 78.8 78.1 79.0 77.9 5 22.3 22.3 33.8 47.4 38.5 48.6 68.4 73.4 71.5 74.4 70.2 78.0 75.4 78.0 79.1 77.9 6 32.0 32.0 32.0 35.9 40.7 68.5 55.5 74.0 72.9 77.9 75.8 77.9 78.1 77.9 78.6 77.8 7 36.4 36.4 45.2 49.7 51. 67.9 47.7 71.8 63.5 77.5 78.1 77.9 79.0 77.8 78.9 77.5
Table IV. AD831 Mixer Table, 5 V Supplies, 1 k Bias Resistor, LO = 20 dBm
LO Level 20.0 dBm, LO Frequency 130.7 MHz, Data File G1T1K 3881 RF Level 0.0 dBm, RF Frequency 120 MHz Temperature Ambient Dut Supply ±3.50 V VPOS Current 59 mA VNEG Current 61 mA Intermodulation table RF harmonics (rows) LO harmonics (columns). First row absolute value of nRF mLO, and second row is the sum. 0 0 1 2 3 4 5 6 7 34.1 34.1 46.6 46.6 41.3 41.3 53.9 53.9 66.9 66.9 77.4 77.4 78.9 78.9 1 60.6 60.6 0.0 27.3 48.8 37.8 58.8 47.9 52.5 61.4 65.8 69.7 73.3 78.6 79.0 78.8 2 52.3 52.3 35.2 28.7 40.1 47.6 59.5 65.2 73.7 70.6 76.6 72.9 73.8 78.7 77.9 78.7 3 16.6 16.6 41.8 20.7 52.2 41.7 41.8 62.5 68.1 76.9 75.2 77.4 78.8 78.6 78.0 78.6 14 4 12.8 12.8 29.8 32.9 57.9 54.2 61.2 64.2 60.3 76.8 65.4 77.7 79.2 78.6 79.3 78.3 5 26.0 26.0 29.1 39.2 38.6 50.4 58.1 73.8 71.0 78.6 70.0 78.5 73.6 78.4 79.5 78.3 6 45.0 45.0 35.3 38.2 45.8 64.1 57.5 72.3 63.4 78.3 73.6 78.4 74.9 78.2 79.3 78.1 7 38.8 38.8 49.0 47.8 47.7 64.9 54.0 72.6 62.3 78.1 68.7 78.2 79.3 78.2 79.3 78.0
REV. C
AD831
Figure 12. Third Order Intercept Characterization Setup
Figure 13. IF-to-RF Isolation Characterization Setup
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AD831
OUTLINE DIMENSIONS
20-Lead Plastic Leaded Chip Carrier [PLCC] (P-20A)
Dimensions shown in inches and (millimeters)
0.048 (1.21) 0.042 (1.07)
3 4 19 18
0.180 (4.57) 0.165 (4.19) 0.056 (1.42) 0.042 (1.07) 0.20 (0.51) MIN 0.021 (0.53) 0.013 (0.33) 0.020 (0.50) R
0.048 (1.21) 0.042 (1.07)
(PINS DOWN) 8 14 9 13
TOP VIEW
0.050 (1.27) BSC
0.330 (8.38) 0.032 (0.81) 0.290 (7.37) 0.026 (0.66) 0.040 (1.01) 0.025 (0.64) 0.120 (3.04) 0.090 (2.29)
BOTTOM VIEW
(PINS UP)
0.020 (0.50) R
0.356 (9.04) 0.350 (8.89) SQ 0.395 (10.02) SQ 0.385 (9.78)
COMPLIANT TO JEDEC STANDARDS MO-047AA CONTROLLING DIMENSIONS ARE IN INCHES; MILLIMETER DIMENSIONS (IN PARENTHESES) ARE ROUNDED-OFF INCH EQUIVALENTS FOR REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN
Revision History
Location 6/03Data Sheet Changed from REV. B to REV. C. Page
Updated format . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . UNIVERSAL Changes to Figure 10 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 11 Updated OUTLINE DIMENSIONS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 16
16
REV. C
C0088206/03(C)